|Elliott Sound Products||Project 36|
Death of Zen (DoZ) - A (Not So) New Class-A Power Amp
Rod Elliott (ESP)
Updated November 2018
Because the quiescent current can be quite unstable with variations in the supply voltage. Normal changes in the AC mains can cause Iq to shift above and below the preset value. A simple modification has been added that virtually eliminates the problem (or reduces it to the point where it is immaterial). This, plus another optional modification to help stabilise the bias current are included on the current Revision-B circuit board.
The Zen - along with Zen improved, son of Zen, Bride of Zen, Second cousin of Zen (or did I imagine that one?) Class-A amp designed by Nelson Pass seems to have become popular. (See references.) I cannot imagine why, since the very concept is flawed in many ways. It has minimal feedback, but that is because it has minimal gain to start with, and appears very simple. Perhaps this is the attraction - but at what price? The capacitors needed for the power supply are massive to try to get rid of hum, and massive means expensive. The 'improved' Zen is a little better, since it uses an inductor (or choke) in the supply - obviously the hum drove someone mad. Inductors are expensive too, and also hard to get, and the capacitance has been doubled in at least one version I have seen - ouch, this is seriously expensive!
Well, actually I can see why it is popular. It satisfies the requirement of many amplifier builders, in that it is simple, stable, and very tolerant of layout and component variations. The sonic characteristics will also appeal to many, due to the valve-like sound (or tube-like, if you prefer). Having looked at the original and many of the 'improvements' currently on the web, I did a few tests of my own and frankly, found the amp lacking in the fidelity department. Hi-Fi this most certainly is not. But ... does it sound good? Apparently so, based on the number of people using (and praising) the Zen, but the feedback I have had on the DoZ so far (and my tests) is also very positive and encouraging. At the time of writing, hundreds of DoZ amplifiers have been made, with comparatively few reported problems. The issues that have been encountered have been addressed in the Revision-A circuit boards which are now shipping.
Nelson Pass quotes Einstein as saying "Everything should be as simple as possible, but no simpler". I agree with this entirely, and quickly realised that the Zen is simpler than it should be for its intended purpose.
Therefore, I have done some serious work on 'Death of Zen', a new Class-A power amplifier that will blow the Zen and all its kin into the weeds, without busting the budget or sacrificing sound quality. Global feedback and a minimum of local feedback ensures a very fast and linear amplifier, using the smallest number of components possible. This is the goal, and the remainder of this section explains why.
Photo of Early Assembled Rev-A Board
Lets look at the basic Zen concept, as shown in Figure 1. A power MOSFET is biased using a pot (needed to correct for different device characteristics) so that the voltage at the drain is about 1/2 the supply voltage. Current is limited using a constant current source, and this needs to be set to provide a current that is higher than the maximum peak current to the speaker. Since the amp is not DC coupled, an output capacitor is needed to keep the DC out of the loudspeakers. An input cap is also needed to stop the source (the preamp, or for my tests, an audio oscillator) from stealing the bias voltage.
Figure 1 - Basic Zen Concept
Now at first sight the idea looks sound (pardon the pun). We do need to do some basic maths to determine the current needed, but this is easy. Using a 35V supply, the bias point will need to be about 1/2 supply (17.5V), and this means that for ideal devices the peak speaker current is ±17.5 / 8 = 2.19A (say 2.2A). It is necessary to add a little more current to ensure that the active device current remains high enough to stay within the linear region, so lets say 2.5 amps.
In theory, the ±17.5V should allow a peak power of 19W, but this is not possible due to the losses in the devices. As a result, the amp is rated at 10W, and this is reasonable. The output resistance (at DC - this is not the same as impedance) of this output stage is easily determined from Ohm's Law, so R = V / I = 17.5 / 2.5 = 7 Ohms. Although this is the resistance, the impedance will be similar, although generally slightly lower. According to some, this is the first fault of the design, since damping factor will be at best 1.14 - this is a little shy of the 100 or more that most audiophiles strive for, but more on this later. With the addition of feedback (and yes, the Zen uses some feedback), the output impedance is quoted as about 1 Ohm.
Most readers of my pages will know by now that I am not a fan of switching MOSFETs for audio, since they are far less linear than bipolar transistors or lateral MOSFETs. To me, this is the first failing, since I fully expected the distortion to be somewhat higher than I would consider acceptable for a ghetto blaster, let alone a hi-fi system. Note that lateral MOSFETs are different from vertical types - the former are intended for audio, the latter for switching.
I proceeded to set up a test, using a suitable MOSFET and comparing it with a transistor in the same circuit configuration. The test setup is shown in Figure 2, and I was able to directly substitute the transistor and MOSFET into the circuit, adjust the bias and run the test. Since I wanted to see distortion components alone, I simply used an 8 Ohm drain / collector load, as this is approximately equivalent to the circuit operating with a current source load and driving a speaker. I kept the operating level lower than normal to ensure that a suitable current reserve remained.
Figure 2 - The Test Setup
In the above, the D.U.T. is the device under test. Emitter, base and collector (or source, gate and drain) are connected as shown. For the power supply, I used my 'monster' supply, which is variable only because I use a Variac (variable voltage transformer) to supply the incoming mains. I used a 22,000µF capacitor for added filtering (it was not enough!), and proceeded to take some measurements.
First step was to set the quiescent voltage with the pot, so I had 1/2 the supply voltage at the drain (I tested the MOSFET circuit first). With an applied DC of 30V, this meant a voltage of 15V, so the current was 1.875A or 28W dissipation (both in transistor and load - for a total of 56W). The hum was higher than I would have liked, but I can make this disappear using the averaging capability on the digital oscilloscope.
Applying a 1kHz sine wave, I could see that the distortion was quite visible at close to clipping, and I was able to operate at a maximum of 6V RMS output before the distortion became too noticeable. I then hooked up my trusty distortion meter to see just how much there was. Remember from the test circuit that I have included a 0.5 Ohm resistor in the source to help linearise the circuit - not to too much avail it seems, since the distortion was measured at 1.58% (after hum removal), and it increased very rapidly if I increased the voltage. Hmmm. This verified my suspicions, but now I needed to test a bipolar transistor in exactly the same test setup to compare the two.
I used a Darlington transistor (I dislike these too, but it was convenient and the extra gain is essential with bipolars), and was able to bias the transistor using the same circuit as before. Again, I applied a signal, and was not at all surprised to see that the maximum voltage before distortion was visible on the oscilloscope was considerably greater, and the output generally looked cleaner right up to the point of clipping. I would expect that a discrete complementary pair (the configuration I always use) will be better, but I was rushing to get this into print, so used the most convenient device to hand. At least this means that I can improve on these figures without too much trouble.
To be completely fair, I tested the distortion at 6V RMS again, and measured 1.03% - a worthwhile improvement I thought. Increasing the output to 8V, the distortion climbed to 1.18% - still less than the MOSFET, and with a much improved voltage swing. At this level, the MOSFET was delivering outrageous amounts of distortion, as it started to clip.
The measured distortions are not entirely fair, because of the distortion waveform. With the MOSFET, the distortion waveform was peaky, with quite sharp transitions (indicating high order harmonics). The RMS value is probably too low, and certainly does not indicate accurately the audible effect of the distortion. By comparison, the bipolar transistor had a very smooth and almost perfect 2nd harmonic, with very little evidence of any high order harmonics at all. Asymmetry in the residual distortion waveform showed that there was also 3rd harmonic distortion, but at a lower level - I think I will have to have a listen to the residual signal to determine the 'musicality' or otherwise of the distortion I measured.
29 Oct - Further Tests
The following day, I decided to buy a MOSFET rather than use the one I had, and selected a MTP3055 as a budget device designed for audio and switching. I still don't know exactly what the other one is supposed to be for, but it shouldn't matter - bipolar transistors can be selected for linearity, but it isn't that big a deal. Not so with MOSFETs as I discovered - the new one was markedly better than the original, but still fails to touch the bipolar. Incidentally, the Darlington bipolar I used was a TIP141, and is designed for switching (lest I be accused of fiddling my results by device selection). I did not retest the 60N06 at the lowest level, but given the other results I could see no point.
Since I now have 3 separate test results, I have tabulated them below.
|Output Voltage (RMS)||TIP141 Darlington||MTP3055E MOSFET||60N06 MOSFET|
It would be useful to carry out these tests with a completely hum free supply so that the distortion is not affected by the supply ripple, but by averaging the measured result with the oscilloscope I believe the results are accurate enough for comparison, especially since the same configuration was used for all tests.
Quite obviously, the bipolar is a winner at low levels (where the distortion is most noticeable), and I am sure that using a nice linear transistor such as the complementary pair, these results would show the superiority of the bipolar transistor even more clearly. Again, as the supply limits are approached and the current through the devices varies the most, the bipolar is again well ahead.
UPDATE: The MTP3055 distortion figures actually are very close to those published by Pass Laboratories for the Zen, so this validates the test circuit I used, and that the figures are not exaggerated in any way. (27 Nov 99)
The next step was to test something close to the final configuration, to see what things had an effect (profound or otherwise) on the performance. I still used the TIP141, knowing that I can improve on this greatly as I progress, although as the final circuit shows I eventually chose not to use a compound pair after all. Figure 3 shows the test circuit, still using the 8 Ohm resistor as a load, but I ran these tests using my bench supply to eliminate the hum problems. All tests were performed at an output of 6V RMS (equivalent to the 8V tests above, due to the lower supply voltage).
Figure 3 - DoZ Test Circuit
This is the basic configuration I will be using for the final design, although there will be some resistor value changes as I get closer to the final circuit, and the load resistor will be replaced by a constant current source. For those who want to try the circuit with a high output impedance, I will also include the modified feedback network.
|STOP ! - Do not build this circuit as a real amplifier. This is a test circuit, designed to verify some basic parameters of the design. The final design is shown in Figure 5.|
Some interesting things came to light during testing, especially when I included the resistor (R6) from base to earth on Q2. With no resistor, I measured a distortion of 0.15%, and this was almost completely 2nd harmonic. There was a very noticeable degradation of the positive going slope on a 10kHz square wave, and a fairly low slew rate resulted. Adding the resistor improved this dramatically, and reduced the distortion to 0.05% - but it was now almost completely 3rd harmonic.
This will create a conundrum for some - would you rather have very low levels of 3rd harmonic distortion, or considerably larger amounts of 2nd harmonics (bearing in mind that the 3rd harmonics are still there). I cannot see any good reason to tolerate any more distortion than is absolutely necessary, so considering the much better slew rate (and therefore high frequency performance), I will be including this in the final design. You might want to leave it out if you want the 2nd harmonics, but I don't think the end result will be very satisfactory.
This is due to the transistor's turn-on and turn-off characteristics becoming more symmetrical by providing a base discharge path, but I did not expect such a large difference. The frequency response extends to over 100kHz at full power (6V RMS for these tests), and square wave response shows that the amp is both fast and stable - and this with a very ordinary switching Darlington. I saw no evidence of measurable distortion above the 3rd - there must be some, but I have no way of measuring it. The 3rd harmonic appears to be an almost perfect sine wave, with some very small variations.
Slew rate is better than 6V/µs (positive going) and over 20V/µs negative going - not as good as some, but I blame the TIP141 for this. I have checked the specs on it, and it is a fairly slow device (like most Darlingtons) as confirmed by these tests.
None of this testing has been done with a circuit board. In all cases I simply bolted the device to a heatsink, and attached the other components as required. Power connections were all made using alligator clip leads. Since I have used exactly the same 'rats-nest' wiring for all testing (including these last tests), and I have not been able to induce additional (or reduced) distortion by moving leads about, the amp looks as if it will be fairly tolerant of assembly methods (all known assembly methods will be superior to what I have done so far).
So, there I was on Saturday (27 Nov 1999), thinking suddenly - "I wonder how the amp would work with a MOSFET instead of the transistor?" Off to the workshop and I tried it. The answer is ... horrible. Apart from the greatly reduced voltage swing because of the topology, the distortion at 1V (125mW into 8 Ohms) was about 0.4%, and I was mightily disappointed.
You see, I really would like to use a MOSFET in an amp that I would like listening to, because the idea appeals to me. They are fast, need minimal drive current, and the overall concept is wonderful. But they still don't sound any good - what a shame. (This applies to vertical MOSFETs - lateral MOSFETs are designed for audio, and are considerably more linear.)
Thus chastened, I thought I would just have a quick muck about with the current source (having re-installed the bipolar transistor) and listen to it on a speaker. Even with the slow TIP141 transistors (I used one for the current source too), the rats-nest wiring I was using instantly caused me problems (clip leads all over the place, and components supported by sky-hooks and each other).
The issues were easily sorted out (re-arrange the clip leads ), and I ran some distortion tests with and without a load. Distortion was almost exactly the same as previous testing, and I was finally able to measure the actual output impedance, which measured at 0.22 Ohms. Not too shabby for such a simple amp.
As for the sound, well I must admit that it sounded just like an amplifier. I couldn't hear any nastiness, and even with the limited power it was quite loud enough. The main problem I have now is that I don't have any conventional hi-fi speakers (mine are fully active), so was forced to listen on one of my lab speakers. Even there I am limited, since the main lab system is tri-amped.
One thing I have realised in all of this testing, is that a Class-A amp is a far more irksome thing to design and test than a Class-AB amp. This is partly because of the high current that is always present (and the fact that massive heatsinks are needed just to do simple testing), and partly because in this design I am trying to achieve maximum performance from minimum components - this has turned out to be more difficult than expected, and some of the simplest changes can make a great difference to the performance.
I am now leaning more and more towards the concept suggested by John Linsley-Hood , where the bias current is modulated to provide Class-A but with less quiescent dissipation. You would be surprised how hot a pair of 1°C/W heatsinks get with a quiescent current of 2.5A and a supply of 40V. Mind you, I did manage to get 18W into 8 Ohms at the onset of clipping, but with the sinks just lying on the bench I had to be careful that the whole amp didn't destroy itself. For further tests, I had to build it properly - what a pain!
So, pretty much having made up my mind on the topology, I set about building the amp. I must say that the final result lived up to nearly all expectations, and works extremely well. One word of warning - I used TO-3 case transistors, and I strongly suggest that you do the same. Most plastic case devices don't have good enough case to heatsink thermal resistance, and with a final dissipation of 28W per device, even the TO-3s get hot. However, the suggested devices shown in Figure 5 (Final Circuit) are the MJL21194 (or MJL4281), and they have proven themselves with many hundreds of DoZ amps built.
For ease of working (and so it would stabilise quickly) I only used a small heatsink, and ran a 12V fan at 6V to keep it cool. At ½ voltage, the fan was very quiet, so you might want to consider this as a possibility for Class-A amps in general.
The semi-final circuit (at least for the time being) for the DoZ is shown in Figure 4, and it can be seen that it is a bit different from the last attempt. This being the full and proper circuit, it is fully functional, and I have tabulated test results below.
After all the experiments I carried out before, it turns out that the current source is more critical than I would have hoped. Although this is a simple circuit, it is supposed to supply a constant current at any frequency, and this is harder than you might imagine. R7 and R8 were added in an attempt to speed up the current source, and were only partially successful. As it stands, the amp will provide full power up to about 16kHz, which is actually more than enough for any application.
For final testing you will need two multimeters, one to measure current and the other for voltage. If you only have one, use a 1 Ohm resistor in series with the power supply positive lead. When you measure 1 Volt, this means that the amp is drawing 1 Amp. The resistor can remain in circuit, providing a useful reduction in supply ripple. You will lose 1.7V at operating current, and a 5W resistor is sufficient - it will get hot though.
Figure 4 - Semi-Final DoZ Circuit
|Q3 and Q5 (the output transistors) must be on a substantial heatsink (see below), and Q2 and Q4 also need heatsinks. These do not need to be especially large - TO-220 U-shape heatsinks will be fine (or make suitable sinks with scrap aluminium). The drivers get excessively hot with no heatsink.|
A quick circuit description is in order. VR1 is used to set the DC voltage at the +ve of C3 to 1/2 the supply voltage (20V for a 40V supply), by setting the voltage at the base of Q1. The 100µF cap ensures that no supply ripple gets into the input. Q1 is the main amplifying device, and also sets the gain by the ratio of R9 and R4. As shown, gain is 13, or 22dB, providing an input sensitivity of about 1V for full output.
Q4 is the buffer for the output transistor Q5, and modulates the current in Q2 and Q3. VR2 is used to set quiescent current, which I found needs to be about 1.7A for best overall performance. C4 and R6 are part of a bootstrap circuit, which ensures that the voltage across R6 remains constant. If the voltage is constant, then so is the current, and this part of the circuit ensures linearity as the output approaches the +ve supply.
After some more testing, I found that the optimum quiescent current was 0.75 times the peak speaker current. At lower currents, third harmonic distortion predominates, while at higher current distortion seems to remain stable (but device dissipation is increased).
You will notice that there is no Zobel network on the output, and the amp is unconditionally stable without it.
Before applying power, set VR1 to the middle of its travel, and VR2 to maximum resistance (minimum current). Be very careful - if you accidentally set VR2 to minimum resistance the amp will probably self destruct - more or less immediately.
With an ammeter (or 1 Ohm resistor) in series with the power supply, apply power, and carefully adjust VR2 until you have about 1A. Set VR1 to get 20V at the +ve of C3, and re-check the current. As the amp warms up, the current will increase, and you need to monitor it until the heatsinks have reached a stable temperature. If necessary, re-adjust VR2 and VR1 once the amp has stabilised. If you use a heatsink of more than 0.5°C/W the amp will overheat and will be thermally unstable - this is not desirable (note use of extreme understatement)
I used a 40V supply, and was able to obtain 20W at the onset of clipping. Clipping is a lot smoother than most solid state amps, and the amp has no bad habits as it clips. Using a 1µF capacitor directly across the output caused no problems, other than some mild overshoot with a square wave input.
As the supply voltage changes with normal variations in AC mains voltage, the quiescent current also shifts. This is not desirable, and is easily solved with the addition of a resistor and a zener diode (or a series string for odd voltages). If you are using a regulated supply, this mod is not needed.
The process is very simple. First, measure the actual nominal supply voltage - the amp(s) must be connected. Subtract 5 to 7 volts from the measured voltage, to obtain a value that can be matched by standard zener diodes. For example, your supply voltage might be 38V, so a zener voltage between 31 and 33 volts is needed. Since 33V is a standard voltage, that will be fine.
The complete updated circuit is shown in Figure 5, and also shows the actual circuit used on the PCB (excluding the modification described here). The voltage for the quiescent current setting and output voltage is now reasonably well fixed, so mains voltage variations will have very little effect on the overall current of the output stage. Minor variations are also prevented from causing slow voltage shifts at the output. These were never audible, as the circuit is deliberately very slow, but eliminating them cannot be a bad thing. The modification requires that one track be cut, and a resistor and zener (or zener string) attached to the underside of the board. Despite the sound of this, it is completely painless :-)
D1 and D2 are zener diodes - you may only need one of them, depending on your supply voltage. The selection process is described fully below. Within the useful range of zeners, the following values are standard and suitable for the purpose ...
10V, 2 x 12V (recommended), 15V, 16V, 18V, 20V, 24V, 30V, 33V
Values higher than 33V are uncommon in retail electronics outlets, and anything lower than 10V is not recommended in a series string for this application. A pair of 12V zeners gives a stabilised voltage of 24V, which is ideal for the normal supply range of 27-35V. R11 is now shown as 330 ohms (it was 1k), which will provide a more stable voltage with the recommended 27V supply.
Figure 5 - The Complete DoZ Schematic (With Iq Stabilisation)
* D1, D2 and R11 should be considered essential. C8 (shown in grey) may be needed with some combinations of semiconductors. It has been found that some P36 amps oscillate due to just the wrong combinations of fT, and adding C8 fixes the problem. Despite the apparently large value of C8, response remains flat to over 100kHz, so response is not affected. C5 and R14 are not located on the PCB.
There are a few other small changes to the circuit, but these are simply to reflect the PCB design and are of no real consequence. A Zobel network has been included - not because the amp needs it, but just in case a reactive load that may cause instability is connected. C5 has been reduced in value so it will fit on the board, and C3 (still very much needed !) is mounted off the board as it is too large for PCB mounting (it would almost double the board size).
C3 should be a minimum of 2,200µF for 8 ohm loads, which gives a -3dB frequency of 9Hz. If 4 ohm operation is intended, C3 should be 4,700µF. Being an electrolytic capacitor, it will introduce some distortion at frequencies below the -3dB frequency, so it needs to be larger than you might imagine. Aim for a value that gives a -3dB frequency at least one octave below the lowest frequency of interest.
A quick calculation example for the zener rating and resistance are in order, so it is properly understood. The maximum zener current for a given voltage is easily calculated ...
Iz = Pz / Vz where Iz is zener current, Pz is the power rating, and Vz is the zener voltage
Small zeners are typically rated at 400mW and 1W. A 12V 400mW zener therefore has a maximum current of 33mA. Allowing for a resistor voltage drop of 3 to 7 volts means that the zener current will be 3 to 7 mA with 1k (1V across 1k gives 1mA), or 9 to 21mA with 330 ohms. Since it is recommended that zeners be operated at between 5% and 80% of the maximum rated current, these values fit very nicely into our requirements. Feel free to re-calculate the value for R11 yourself, aiming for a zener current of about 10mA or so.
The total zener voltage of should be 24V, so two 12V zeners are the most appropriate. Try to ensure that the zener current is at least 5% of the maximum, or the regulation will not be as good as it should be. Use a pair of 12V zeners in preference to one high voltage and one low voltage.
The modification described here does not change the measured performance of the amp, and creates no audible differences whatsoever. It is designed to stabilise the quiescent voltage and current, and it does that quite well. Some small variations will still be measured, but are so reduced in magnitude as to be considered negligible for all practical purposes.
On the basis of the tests, I would rate this amp at 15W, although I did get more. Distortion rises with increasing level, and starts to get a bit high above 15W - at low power (such as a couple of watts) the distortion was about the same as the residual of my oscillator, which means that it must be below 0.04%, but I have no idea just how low it gets. All distortion components are predominantly second harmonic at all tested levels.
I simply used components as I found them, and did no matching or any selection. All test results are based on the prototype, which uses ordinary resistors, a couple of old salvaged computer caps for the high values, and standard electrolytics for the others. The input capacitor is an MKT polyester type.
|Maximum power 8 Ohms||20W (15W)|
|Output Noise (unweighted)||<1 mV|
|Distortion @ 1kHz, 15W||< 0.2%|
|Output Impedance||0.378 Ohm|
|Frequency Response (-0.5dB @ 1W)||<10Hz to >50kHz|
Note: Although I tested with a 40V supply, this is not recommended. The typical supply voltage should be no more than 30V.
I could hear no noise at all, even with power supply ripple of 300mV peak-to-peak. The noise level I measured was about 0.5mV, but it is not easy to measure accurately at such low levels. There appeared to be no residual hum that I could see on the oscilloscope, even with averaging turned on.
From this it appears that the amp is quite tolerant of supply ripple, and a simple supply will probably be fine. I tested with my normal 'monster' supply, which has a fair bit of ripple, and still could not measure any supply hum at the output. A suitable power supply would be the capacitance multiplier circuit (Project 15), or a simpler one can be used.
The amp is extremely tolerant of voltage, so for less power, use a lower voltage supply - no other changes are necessary. I found that the amp worked perfectly with supplies down to 15V, but less than 20V DC is unlikely to be useful (this will only give about 4.5 Watts into 8 Ohms).
Do not try to increase the power by using a higher voltage, as the dissipation in the transistors will exceed their ratings. If you need more than 15W, I strongly suggest that you use a circuit such as the 60W amp (Project 3A), which actually has lower distortion than this design.
The amp will also tolerate a short circuit with no ill effects (I wouldn't keep it up for too long though), and even (blush) reverse polarity. I accidentally connected the supply up backwards while testing, and thought "Oh, no. Now I'll have to rebuild the blessed thing" (if the truth be known I thought something much shorter!). However, I connected the supply the right way 'round, and away it went, as if nothing had ever happened. This is not an experiment I suggest to others.
I found that the design is also unaffected by quite a few component variations. When I first started testing there were no emitter-base resistors in the current source, and when I added them, I simply readjusted the two pots to get everything back where it was. I retested distortion after making the changes, and could measure no difference.
Before I finish with this project, I have tried some faster transistors (see below). The ones I used initially are the absolute base model 2N3055/1, so I tested with something faster (but with less power - I used plastic 130W devices). The 2N3055 comes in a whole bunch of different flavours - fast, slow, 60V, 100V etc. The ones I have are slow (FT is only 800kHz) 60V devices (I salvaged them from a bunch of old power supplies).
I do not suggest that you use plastic case transistors unless the supply voltage is kept below 35V, or if you must use low power plastic cased devices (such as TIP3055s) use two transistors in parallel. The latter method will make a nice simple amp quite complex. Otherwise, you can use MJL4281 or MJL21194 transistors. These are very nice devices, and have a sufficiently high power rating so that parallel operation is unnecessary. These are the recommended power transistors. TO3 devices can be used, but must be mounted off-board (keep leads very short).
I tried transistors with an fT of 2.5MHz, and it made only a slight difference to the speed of the amp (slight, as in not worth the effort). Distortion remained about the same, and the amp remained stable.
I also tested the amp into 4 Ohms while still set up for 8 Ohms, and it managed 10W at a distortion of about 0.4% (far too high for my liking). I had to reduce the voltage and increase current so it clipped symmetrically. I have prepared a table of voltage, current, impedance and expected power below for those who want to experiment further.
|Z (ohms)||Volts||Iq (Amps)||Diss. (W)||Power|
|4||40 (NR)||4.00||160.00 (NR)||30.04|
The table is not meant to be too accurate, but as a guide only (the figures were calculated in a spreadsheet, using a fairly basic empirical formula). Note that with a dissipation of 160W, 4 Ohm operation from a 40V supply is not recommended. Trying to get a continuous 68W of heat out of each transistor and into a heatsink is extremely difficult, even with TO-3 transistors. Even 34W each requires meticulous attention to detail with the transistor mounting if you want to keep the thermal resistance (and hence temperature) down. Values shown with a star (*) are too high and should be avoided altogether. It will simply be too hard to maintain a sensible transistor temperature. For use with 4 ohm loads, a 25V supply should be considered (about 9W typical).
The voltages shown will be highly dependent on the transformer you use. For example, a 27V supply is shown, and that's what you'll get using a 25V transformer secondary, based on the use of a 300VA transformer. Around 19V DC is available from an 18V transformer, although it will be a little higher if the quiescent current is reduced down to 0.95A (1A near enough) for use into an 8 ohm load. It's impractical to try to cover every combination of transformer secondary voltage and quiescent current.
If you can't keep your fingers on transistors, then they are hotter than I like to operate them - I know they will take much more, but it shortens their life.
In reality, the amp can be operated into any impedance you like, while still set up for 8 Ohm operation. Just remember that for lower impedances, the output will not clip symmetrically, and output power is reduced. At higher impedance, the power is reduced, but so is distortion.
|One problem with such a simple design is that the quiescent current is supply voltage dependent, even with the bias stabilisation circuit. Mostly this will not cause major problems, particularly if a generous heatsink has been used (and why would you use anything else?). It does require that the current is set carefully, and should be monitored carefully after you complete the amp to make sure it cannot reach destructive levels.|
As I have said before, this amp needs a really, really good heatsink, as do all Class-A amplifiers. Have a look at my article on heatsinks to see what sort of radiating surface is best. A thin coat of flat black enamel paint seems to be the most effective in my experience (other than black anodising, which is the overall winner).
While the supply is basically straightforward, I've added the supply options. The first is a simple transformer, bridge rectifier and smoothing capacitor. It's nothing fancy, but will power a pair of P39 amplifiers happily. The transformer needs to be rated for 300VA. In theory, you can get away with a slightly smaller transformer, but then the supply voltage will be quite a bit lower than expected because of the transformer's regulation. Even with a 300VA tranny you won't get as much output as you might imagine, it will be quite a bit less. With a 25V secondary, expect about 32V when loaded with two channels (each drawing 1.6A quiescent).
The ideal supply voltage is about 27V DC, and this should be achieved easily with a 25V transformer. Although there are references to supply voltages up to 40V, this is absolutely not recommended for normal use. DoZ is not about providing 'lots of watts' - it's designed as a simple and reliable Class-A amplifier, and even 35V operation is not a good idea at all. A 27V supply is realistically at the top end of the recommended options. The only exception is if you are using a 16 ohm load, but these are very uncommon these days.
Normally you'd expect a DC voltage of around 35V from a 25V transformer, but that won't happen with a continuous high current load. A 300VA transformer will have a primary resistance of around 5 ohms, and a secondary resistance of up to 0.5 ohm. The peak rectifier current is around 12A for a 3.2A DC load with the supply shown, and coupled with the winding and diode forward resistances you will actually get around 27V DC as noted. It doesn't take much resistance to cause a large voltage drop when peak currents are so high. The alternative is to use a lower secondary voltage. Yes, you don't get as much power, but DoZ is not designed to be a 'powerhouse' - it's Class-A. Reducing the transformer secondary voltage to 20V is a good idea, although that reduces power output to about 7W. This might well be enough for many applications.
Figure 6 - Basic Power Supply
Using a 25V transformer, the input current to the bridge rectifier will be over 5.5A, giving a total of at least 165VA. The transformer must not be rated lower than that or it will overheat and fail. Using the 0.1 ohm resistor (R1) provides a useful reduction in ripple voltage, but if you really want the lowest possible ripple from a simple supply then use a 10mH inductor instead. It needs to be rated for a minimum of 5A, and the DC resistance should not exceed 0.1 ohm if possible. DC ripple voltage with only the resistor will be about 300mV RMS, reduced to around 20mV RMS with a 10mH inductor. You can also increase the value of R1, both to reduce the supply voltage and reduce ripple voltage. A 10W resistor is recommended if it's more than 0.1 ohm.
You can duplicate R1 and C2, so each section powers its own channel independently. The same can be done if you use the 10mH inductor, and that will reduce the ripple voltage at the DC output and keep the two amps separated. You can also build the power supply as 'dual mono' - a completely separate power supply for each amplifier. The transformers can then be downgraded to 160VA types, and there is no interaction between the channels. It's a very expensive option though, and it's highly unlikely that you will hear the slightest difference.
Figure 7 - Capacitance Multiplier
The alternative is to use a capacitance multiplier. A representative drawing is shown above, and it's capable of reducing the ripple voltage to less than one millivolt. The disadvantage is that you lose a bit more voltage and have an additional heat source in the two transistors. These must be on a heatsink, and the pair will dissipate about 10W. Output voltage will be about 24V DC with a 25V transformer. A 30V transformer secondary allows for a greater drop across the capacitance multiplier, but you'll get an output voltage of around +27V. The transformer needs to be 300VA as before. Larger transformers can be used for either supply if desired, and voltages will be a little higher. If you prefer, you can use a separate capacitance multiplier for each channel.
Voltage shown on all diagrams are nominal, and they will vary depending on the quality of the transformer used and the mains voltage at the time (it varies by at least ±5% in all locations).
From everything that has gone on during development, I feel that my anti-MOSFET (at least for switching types) stance is justified for a Class-A design, and that the concept of such an ultra simple amplifier is flawed if low distortion is the ultimate goal. Certainly, some degree of low order harmonic distortion is not necessarily unpleasant, and may even add some degree of musicality to an otherwise 'clinical' sound, but the cost (i.e. loss of definition of complex passages, etc.) due to intermodulation distortion is way too high for my liking.
Even the bipolar transistor version is unacceptable in the most basic configuration, since although the distortion is lower, it is still too high - this does not qualify as hi-fi by any definition. The addition of global negative feedback (as shown in Figure 3) is the ONLY way to reduce the distortion to within acceptable limits.
In the introduction, I said that I would discuss the damping factor issue further, and so I shall. In my article on impedance (see references), I went into some detail about one of my amps that I modified to have a very high (about 200 Ohms) output impedance (this is something I've done for various reasons for many, many years). The overwhelming majority of people who heard it said that it sounded just like a valve amp - but what is the sound of a valve amp when its at home?
Firstly, I have to disagree with the 'overwhelming majority' to some extent. There are other subtle differences between my modified amp and a valve amp that cannot easily be eliminated. As long as the level is reasonably low (not even thinking about clipping), these differences may be difficult to detect by ear, but include:
|Valve Amp||Modified Transistor Amp|
|Increasing distortion with level (> 0.05% and rising)||Relatively constant distortion (< 0.01%)|
|Distortion is almost all low order||Some higher order components|
|Medium output impedance (about 2 to 6 Ohms, typically)||Very high output impedance (> 200 Ohms)|
|Relatively low bandwidth||Wide bandwidth|
The output impedance is by far the most noticeable effect, and results in apparent better bass (but not always - it is sometimes peaky and with some speaker systems becomes 'flabby'), and also an improvement in high frequency performance. As the impedance of a speaker rises - either at low frequencies as it approaches resonance, or at high frequencies due to the inductance of the voice coil - a normal amp simply delivers less power. This is because if the voltage is fixed (by the gain of the amp), then less power is delivered to a higher impedance than a lower impedance.
Likewise, where there are impedance dips - often caused by crossover networks - the 'normal' (i.e. voltage) amp will deliver more power, often to the detriment of the acoustic balance. An amp with a high(ish) impedance can be thought of as a constant power device - for any given input voltage, the power will remain constant regardless of variations of load impedance. This is not strictly true, of course. No amp can be tailored so the output impedance is just exactly right to give equal power regardless of impedance, but you can get passably close.
What this means is that the speakers will provide more output at frequencies you are unused to hearing from them, and less where they might have sounded too prominent. The overall sound is not always more accurate (often less so), but it is different, and will generally seem to sound better. If my tests are any guide (I hope so!), then some speakers actually benefit from a small amount of induced output impedance (typically around 8 ohms), and I am using this technique on my own system for the bass and midrange drivers.
Indeed, Nelson Pass mentions this very point, and advises that some speakers will not like the output impedance of the Zen, and will not sound the way they should.
The Zen (and all derivatives thereof) will produce exactly this phenomenon, and I suspect that this is one of the main attractions. If this is the case, the DoZ amplifier should be just what you are looking for. Although marginally more complex than the Zen, it will provide pure Class-A at acceptably low distortion levels.
I aimed for an output power of at least 10 Watts (Wow - that much!), obtained 19W (but at a voltage that cannot be recommended), and this will require some fairly large heatsinks to keep temperatures down to reasonable levels. The power supply is much cheaper than that of the Zen, and can use a basic supply or a capacitance multiplier to eliminate ripple, without sending the builder broke with the cost of multiple high value capacitors. The output is capacitor coupled, allowing a simple single supply and no DC servos to try to minimise the DC offset.
I have also designed a simple, high performance preamp circuit (all discrete Class-A), which looks pretty good so far (it has been built and tested - see Project 37). Simulations of this indicated that I will be completely unable to measure the distortion (less than 0.0001%) because it is so far below the limits of my equipment. The reality is a little different, but the distortion is still very low, and frequency response is very good indeed.
Both the power and preamp are completely new designs, but due to the limited number of sensible amplifier topologies, will almost certainly look like something you have seen already. I have yet to include (as an option) the ability to increase the output impedance up to about 8 Ohms, so you can have the one benefit of the Zen approach without the shortcomings.
NOTE:I have not published (and do not intend to) the circuit for the Zen amp. It is not my intellectual property and to reproduce it here is not my policy. A web search for "zen" will find it (along with 10,000+ other sites), or you can just go to the Nelson Pass site. This will not show all the variations, but the idea is much the same for all of them.
|Copyright Notice. This article, including but not limited to all text and diagrams, is the intellectual property of Rod Elliott, and is Copyright © 1999. Reproduction or re-publication by any means whatsoever, whether electronic, mechanical or electro- mechanical, is strictly prohibited under International Copyright laws. The author (Rod Elliott) grants the reader the right to use this information for personal use only, and further allows that one (1) copy may be made for reference while constructing the project. Commercial use is prohibited without express written authorisation from Rod Elliott.|